• 专利附录
  • 专利说明
  • 权利要求
  • 类似技术
  • 同族专利
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  • 优先权
    • 专利摘要:
    In order to enable full-bridge DC / DC converter (1) with phase shift control switching at zero voltage (ZVS), without having to provide an additional inductance, it is provided that before switching to a passive phase of the full bridge (2) in the secondary side Output rectifier (5) a short circuit is generated, which causes by the resulting short-circuit current (ik) via the secondary side of the transformer (T), an increase of the primary current (ip) via the primary side of the transformer (T).
    公开号:AT515242A1
    申请号:T50845/2013
    申请日:2013-12-20
    公开日:2015-07-15
    发明作者:Allan Sanchez；Josef Möseneder；Andreas Ehrengruber
    申请人:Fronius Int Gmbh；
    IPC主号:
    专利说明:

    Method for controlling a full bridge DC / DC converter
    The subject invention relates to a method for controlling a full bridge DC / DC converter having a primary-side full bridge and a secondary output rectifier, which are interconnected by a transformer, the full bridge with the arranged in the two bridge arms two series Schal¬ consecutively and successively through a positive active phase, a positive passive phase, a negative active phase and a negative passive phase is switched through, with alternating active and passive phases.
    Full bridges DC / DC converters (so-called full-bridge converters) consist on the primary side of a full bridge with two bridge branches, each with two semiconductor switches (usually designed as FET, MOSFET or IGBT). Between the semiconductor switches each Brücken¬zweiges the primary side of a transformer is connected. The secondary side of the transformer is connected to a secondary-side rectifier in any desired embodiment, for example as a synchronous rectifier with a mid-point circuit and active switches or as a mid-point rectifier with diodes. A load is connected to the secondary side rectifier. Such full bridge DC / DC converters are well known. In a full bridge DC / DC converter with phase control (so-called full-bridge phase shift converter), the output voltage is controlled by the phase position of the rectangular voltages of the two bridge arms of the primary-side full bridge is regulated together. The duty cycle of the two bridge branches is preferably 50%, reduced by a constant or variable dead time. In order to reduce the switching loss of the semiconductor switches, switching at zero voltage (so-called zero voltage switching, ZVS) may also be provided. The functioning of ZVS is well known, which is why it will not be discussed further here. For this purpose, in each case a capacitor and a diode are connected in parallel to the individual semiconductor switches of the full bridge. A full-bridge FET semiconductor switch is known to have a parallel intrinsic body diode and a parasitic output capacitance, which can also be used for zero voltage switching. Such a full bridge DC / DC converter with phasing control and VSV is e.g. from US 2013/0223103 A1.
    At low load and resulting low primary current iP, in conventional full-bridge DC / DC converters with phasing control and ZVS switching at zero voltage is known to be impossible or only possible to a limited extent. This is because at low load, there is not enough energy (stored in inductor L by primary current iP according to E = 1/2-L-iP2) to fully charge and discharge the switch capacitances, which is necessary for ZVS. To resolve this issue, are in the state of
    Technique various measures proposed. Some are based on introducing in some way an additional inductance as an energy store to use the stored extra energy at low load for switching at zero voltage. Examples of these are the above-mentioned US 2013/0223103 A1 or US Pat. No. 5,563,775 A. However, the additional inductance generally requires additional installation space, causes additional costs and is therefore disadvantageous.
    It is therefore an object of the subject invention to provide a full bridge DC / DC converter with phasing and ZVS, which allows for the semiconductor switches of the full bridge without additional inductance switching at zero voltage (ZVS) even at nied¬rigen loads.
    This object is achieved according to the invention in that before switching to a passive phase in the secondary-side output rectifier, a short circuit is generated which causes an increase of the primary current via the primary side of the transformer by the resulting short-circuit current via the secondary side of the transformer. This short-circuit current forces an increase in the primary current on the primary side of the transformer, which in turn causes an increase in the currents through the capacitances of the switches. The additional current is sufficient to fully charge and discharge the capacitances of the switches and therefore to realize ZVS. The increase of the primary current does not affect the load L of the full bridge DC / DC converter.
    In order to prevent harmful voltage spikes at the switches of the output rectifier, the short circuit in the output rectifier is advantageously canceled before switching to the following active phase.
    Preferably, the short circuit is sustained during the passive phase to store sufficient energy in the leakage inductance of the transformer through the increased primary current for subsequent switching in the full bridge so as to ensure switching at zero voltage.
    In order to prevent an excessive increase of the primary current, the short circuit is preferably generated after the termination of the preceding active phase.
    In the case of negative output currents, the switch-on time duration of the switches of the first bridge branch or of the second bridge branch can be reduced for a transition to a blocking mode of the full-bridge DC / DC converter. In this way, the size of the negative output currents can be limited to an acceptable and reliable level in a simple manner.
    Preferably, in the blocking mode, the short circuit is generated in the secondary side output rectifier during a passive phase to ensure that the active phase is not interrupted by the switching in the output rectifier, which would be detrimental to the blocking mode. For a transition from the blocking mode to a normal operation of the full-bridge DC / DC converter, the turn-on time of the switches of the first bridge branch or of the second bridge branch is advantageously increased. This can be easily switched from lock mode to full load of full bridge DC / DC converter. For partial load, for a transition from lock mode to normal operation of the full bridge DC / DC converter, the turn-on times of the switches of the first bridge branch or the second bridge branch are advantageously set earlier in time. This shortens the active switching phases of the full bridge DC / DC converter 1, which forces the control unit of the full bridge DC / DC converter to correct the phase position in order to achieve the desired output voltage. This can be repeated until the desired duty cycle in the full bridge of the full bridge DC / DC converter of 50% is reached.
    The subject invention will be explained in more detail below with reference to Figures 1 to ..., which show by way of example, schematically and not limiting advantageous Ausgestal¬tungen the invention. It shows
    1 is a full bridge DC / DC converter,
    FIG. 2 shows a typical characteristic of the output current and of the primary current of a full-bridge DC / DC converter as a function of the phase position, FIG.
    3 to 9 switching phases of the full bridge DC / DC converter in normal operation in a control according to the invention,
    10 shows the switching points of the switches of the output rectifier in a erfindungs¬gemäßen control,
    11 shows a characteristic of the output current and of the primary current of a full-bridge DC / DC converter as a function of the phase position which is desired for certain applications,
    12 shows the reduced duty cycle of the switches of a bridge branch of the full bridge in the blocking mode,
    13 to 20 switching phases of the full bridge DC / DC converter in the lock mode in a control according to the invention and
    Figure 21 shows the switching of the full bridge DC / DC converter from the lock mode to the normal mode.
    In Fig. 1, an inventive full bridge DC / DC converter 1 with phasing and switching at zero position (ZVS) is shown. The primary-side full bridge 2 is connected to the input side of a DC voltage source VDC and it can be provided at the input and a smoothing capacitor Cin. The full bridge 2 consists of two bridge branches 3a, 3b with two switches S1, S2 connected in series in the bridge branch 3a and two switches S3, S4 connected in series in the bridge branch 3b. The switches S1, S2, S3, S4 can be used as semiconductor switches, e.g. be implemented as FET, MOSFET, IGBT, etc. The switches S1, S2, S3, S4 are controlled by a control unit S, as indicated in Fig. 1. A diode D1, D2, D3, D4 and a capacitor C1, C2, C3, C4 are arranged in parallel with the switches S1, S2, S3, S4 (in the case of semiconductor switches, as a rule, formed from the intrinsic body diode and parasitic output capacitance) in conjunction with the leakage inductance L | k and the main inductance Lh of the transformer T, realizing switching at zero position (ZVS). Between the switches S1, S2 and S3, S4 of each bridge branch 3a, 3b bridging tap points A, B are provided.
    As is customary, the primary side of the transformer T is connected between the bridge branches A, B between the two bridge branches 3a, 3b, so that the primary current iP flows through the primary winding of the transformer connected between the bridge tap points A, B. The secondary side of the transformer T is connected to an output rectifier 5, here in the form of a synchronous rectifier. The output rectifier 5 is designed here as Mit¬telpunkt circuit 4 with two rectifier branches 4a, 4b, each with a switch S5, S6und with an output inductance L0. The switches S5, S6 may in turn be used as semiconductor switches, e.g. as FET, MOSFET, IGBT, etc., and can be controlled by a control unit S again. Optional, but usually, e.g. As a filter, desired, in the output rectifier 5 after the Ausgangsinduktivität L0 also a smoothing capacitor C0 be provided. To the secondary side output rectifier 5 is connected an electric load L through which the output current Iout flows.
    During phase angle control, the switch-on duration of the switches S1, S2, S3, S4 of the two bridge branches 3a, 3b of the full bridge 2 is preferably kept constant at 50% (less a dead time). By the phase position PS of the rectangular voltages in the Brücken¬zweigen 3a, 3b, the output voltage Uout is set, which depends on the LastL, such as. a battery, a welding arc, an electrical device, etc., leads to a Aus¬gangstrom lout and a primary current iP.
    Such a full bridge DC / DC converter 1 with phasing control and ZVS can e.g. in a switched mode power supply, as a power source for a welder or in a battery charger. 2 shows by way of example the typical characteristic of the output current
    L ... rnhptn'i nnrl Hps Primary StrnmPR In, UintprO ipwpilR in Ahhanninkpit nn rlpr Phacpnlanp PR when using the full bridge DC / DC converter 1 with phasing and ZVS as a battery charger, ie with a capacitive load L. The significant kink in the Output current characteristic results from the transition from discontinuous current flow in the output choke L0 (discontinuous conduction mode, DCM) to the continuous flow of current in the output choke L0 (continuous conduction mode, CCM). DCM is spielsweise, because a charger must maintain the battery voltage even after the main charging sequence. Therefore, the charger and thus the full bridge DC / DC converter 1 must be able to supply even small output currents lout (DCM). However, such nied¬rigen currents are not sufficient to realize switching at zero voltage in the switches S1, S2, S3, S4 of the full bridge 2. Of course, similar problems may also occur in other applications of a full bridge DC / DC converter 1 with phasing control and ZVS.
    In the following, the individual switching phases of a full-bridge DC / DC converter 1 with phasing control and ZVS will be described with reference to FIGS. 3 to 9, and the present invention will also be explained. Basically, in the active switching phase, power is transmitted from the primary side of the full-bridge DC / DC converter 1 to the secondary side of the full bridge DC / DC converter 1, and no power is transmitted during the passive switching phase (also called freewheeling phase). In FIGS. 3, 5 to 9, and also 13, 14 to 20, the transformer T is illustrated divided for the sake of simplicity, ie the primary side of the full bridge DC / DC converter 1, separated from the secondary side of the full bridge DC / DC converter 1 ,
    3 shows the positive active switching phase of the full bridge DC / DC converter 1 between the time ti and t2 and Figure 4 shows the associated switch positions of the switches S1, S2, S3, S4, S5, S6, and the time course of the primary current ip. Here, the switches S1 and S4 of the full-bridge 2 are closed and the switch S5 of the output rectifier 5 is closed and the switch S6 of the output rectifier 5 is opened. For better visualization, the switches S5, S6 are shown with different amplitudes in FIG. This leads to a current flow of the primary current iP through the primary side of the transformer T and to an output current lout.
    The transition from the active to passive positive switching phase at time t2 is shown in Figs. 5 and 6 in conjunction with Fig. 4. This transition phase is initiated at time t2 by opening the switch S1 of the first bridge branch 3a. At low load L, the primary current iP would be too low to fully charge the capacitor C1 at the switch S1 by the resulting current iCi and to completely discharge the capacitance C2 at the switch S2 by the resulting current iC2. Thus ZVS at low load L nirht rpalisiprt wprrlpn Ilm rlpm nr7i ihpi inpn confused in rlipspr I Ihprnannsnhasp 71 in 7pitnnnkt t2 on the secondary side of the full bridge DC / DC converter 1, in the secondary-side output rectifier 5 generates a short circuit, the one additional short-circuit current iK on the secondary side of the transformer T causes. The short-circuit current iK circulates in the output rectifier 5 via the rectifier branches 4a, 4b and the secondary side of the transformer T. This is achieved in the embodiment shown by also closing the switch S6 of the output rectifier 5 (FIG. 6). The additional short-circuit current iK circulates through the secondary side of the transformer T, the switch S5 and the switch S6. If the capacitances C1, C2 are not fully discharged or charged, the short circuit will be present if there is still voltage on the primary side of the transformer Tan. This short-circuit current iK therefore forces, on the primary side of the transformer, an increase of the primary current ip about the current iP ', which in turn causes an increase of the currents through the capacitances C1 and C2 by iCi' and C2. The additional current iP 'is limited by the leakage inductance L | k. The resulting currents (iCi + ici ') and (ic2 + ic2') over the capacitances C1, C2 are sufficient to fully charge and discharge them and therefore to realize ZVS. Increasing the primary current iP to iP 'does not affect the load L, since the additional short-circuit current iK circulates in the output rectifier 5 on the secondary side.
    In the following positive passive phase in the period t2 to t3, the switch S2 of the first bridge branch 3a is closed and the capacitance C1 is fully charged (FIG. 7, FIG. 4). However, the short circuit on the secondary side through both closed switches S5, S6 of the output rectifier 5 preferably remains upright, as a result of which the short-circuit current iK continues to flow. As a result, additional energy in the leakage inductance Lik of the transformer T is stored by the additional primary current iP 'which continues to flow. In this phase, the transformer T of the full bridge 2 is in the short-circuit phase due to the turned-on switch S2 and the conducting diode D2, as shown in FIG.
    During the transition from the positive passive phase to the negative active phase at the time t3, the switch S4 is opened in the second bridge branch 3b and the switch S3 is closed, as will be described with reference to FIG. At the same time, the switch S5 in the output rectifier 5 on the secondary side of the full bridge DC / DC converter 1 is opened and the switch S6 remains closed. Thus, the short circuit in the secondary side output rectifier 5 is terminated. The additional energy stored in the previous phase by the increased primary current Pi 'in the leakage inductance Lik on the primary side of the full-bridge DC / DC converter 1 is used to safely completely discharge the capacitance C3 and to safely completely charge the capacitor C4. in order to realize ZVS during switching, even at low loads L.
    In the subsequent after switching of the switches S4, S3 negative active phase in the period between t3 and t4 (Figure 9), the switches S3, S2 are closed in the full bridge 2 and the switch S6 of the output rectifier 5 is closed.
    In the now following reverse transition from the negative active phase into the negative passive phase and further into the positive active phase (as in FIG. 3), a short circuit in the secondary-side rectifier 5 is effected in the period U to t5 in an analogous manner as described above in order to ZVS during switching the switch S1, S2, S3, S4 to be able to Lrealisieren even at low loads. This allows the switching cycle to be repeated.
    In order to realize the invention, the output rectifier 5 must be actively controlled depending on the switching state of the full bridge 2 to make the short at the required times. Basically, in the transition from an active switching phase, characterized by diametrically (with respect to the bridging tap points A, B) in the bridge branches 3a, 3b, closed switches S1 and S4 or S2 and S3 to a passive switching phase characterized by juxtaposition (relative to the bridge tap points A, B) closed switches S1 and S3 or S2 and S4, a short circuit be erzeugzeug. In the case of the reverse transition from a passive switching phase to an active switching phase, the short circuit must be canceled again. During a passive switching phase, the short circuit preferably remains upright.
    In the exemplary embodiment shown, the switches S5, S6 of the secondary-side output rectifier 5, here in the form of a synchronous rectifier, are actively controlled, e.g. from a control unit S. Here, the turn-on points of the switches S5, S6 are synchronized with the switch points of the switches S1, S2, S3, S4 of the full-bridge 2 as described below, in order to implement ZVS.
    The switches S1, S2 and S3, S4 of the two bridge arms 3a, 3b are known not to switch at exactly the same time, but with a switching delay V, typically in the ns range, e.g. 100ns to 300ns, as shown in FIG. The switch-on point of the switch S5, S6 of the output rectifier 5, which effects the short-circuit on the secondary side, must be synchronized with the switch-off instant of the respective switch S1, S2, S3, S4 of the full bridge 2, as in FIG , S2 and S6. The optimum switch-on point SP1 for the switch S6 of the secondary-side output rectifier 5 is in the range of the switching delay V between the switches S1, S2 of the first bridge branch 3a (corresponding to Fig.6, Fig.4). The optimum switch-on point SP1 thus lies in the transition phase from the active to the passive phase, ie after the active phase has ended by opening the switch S1 and before the passive phase has started by closing the switch S2. A switch-on time SP2 before switching off the switch S1, ie before the active phase was ended, would lead to a higher additional primary current iP '. A switch-on time SP3 after the switch S2 has been switched on, ie after the passive phase has been started, ZVS would prevent low loads and therefore should be avoided in any case. The same applies analogously also for the switch-on points of the switch S5.
    The turn-off timings of the switches S5, S6 of the secondary-side output rectifier 5 are preferably set at or in the vicinity of a current zero-crossing of the current through the switches S5, S6. Too early a turn-off time would increase the time period in which the body diode conducts switches S5, S6, which would result in a loss of efficiency due to higher conduction losses, and would further increase the lock delay time of the body diode the switch S5, S6 lead, which would lead to higher losses and higher voltage peaks at the switches S5, S6. A too late switch-off point would lead to a short-circuit on the secondary side, while the primary side is in the positive or negative active phase. This would lead to high primary currents iP and high diP / dt, which in turn would lead to undesirable voltage peaks at the switches S5, S6 of the secondary-side rectifier, which can also destroy the switches S5, S6.
    In the case of a load L, which may also serve as a voltage source, e.g. a battery, may also give a negative output current lout, as shown in Figure 11 with output current louti and primary current IP1. In this case, current flows from the output of the full bridge DC / DC converter 1 to the voltage source VDC, or to the smoothing capacitor 0, η. This can also lead to over-voltage on the smoothing capacitor Cin, which is undesirable. In contrast to this, it is immediately obvious that such an operating mode, especially when using the full-bridge DC / DC converter 1 in a battery charger, would be counterproductive due to the discharge of the battery and therefore should be avoided.
    There are therefore applications of a full-bridge DC / DC converter 1 in which a negative output current lout, the so-called regenerative operating mode, should basically be avoided or at least reduced. Desirable here is therefore a Ausgangsstromcharak¬teristik as shown in Fig. 11 with lout2 and lP2 is shown. This is characterized by a blocking mode BM (blocking mode) of the full-bridge DC / DC converter 1, which ensures that the negative output current Iout is reduced to an acceptable and safe size.
    In order to achieve the desired output current characteristic as shown in FIG. 11, in the blocking mode BM of the full bridge DC / DC converter 1, the duty cycle of the switches S1, S2 in the first bridge branch 3a of the full bridge 2 is drastically reduced, preferably to a value between zero and the minimum possible duty cycle Dmin, which is essentially predetermined by the specification of the switch S1, S2 in terms of the switching time. Normal switch-on durations D of switches S1, S2 used are in the range of> 70ns. The switches S3, S4 of the second bridge branch 3b continue to operate as described above. This is exemplified in FIG. The switch-on times and switch-off times of the switches S5, S6 of the rectifier 5 are also set as described above, ie synchronized to the switches S1, S2. Of course, instead of the switch-on duration D of the switches S1, S2 of the first bridge branch 3a, the switch-on duration of the switch S3, S4, of the second bridge branch 3b could also be reduced. In this case, the switches S1, S2 of the first bridge branch 3a would be switched as in a standard full bridge 2 with phase control.
    The effect of this measure will now be described below with reference to FIGS. 13 to 20 assuming a negative output current Iout.
    FIG. 13 shows the positive active switching phase in the blocking mode BM in the period between U and t2. In FIG. 14, the time profile of the output current Ut, the primary current iP and the switching positions of the switches S3, S4, S5, S6 is again shown. The switches S1, S2 are assumed to be open throughout (duty cycle D = 0) for convenience of description herein. The switch S4 of the second bridge branch 3b and the switch S5 of the output rectifier 5 are closed when the switch S3 is open. Via the conducting diode D1 of the first switch S1, the primary current IP driven by the negative output current outflow flows to the DC voltage source VDC. However, the voltage applied to the smoothing capacitor Cin is also applied to the primary side of the transformer T, which forces a positive slope of the output current Iout, thereby decreasing it. Likewise, the negative primary current iP decreases in this period ti -12, which ultimately leads to the primary current iP changing the sign, as indicated in FIG. 15. Since switch S1 is open, capacitor C1 is charged by primary current iP and capacitor C2 is discharged. By discharging the capacitance C2, the diode D2 of the switch S2 becomes conductive, which at the time t2 the transition from the active positive to the positive passive Schalt¬ phase of the lock mode BM, which is shown in Fig. 16 in the period from t2 to t3, As soon as the primary current iP has changed direction, the switch S6 of the output rectifier 5 can be closed with the switch S5 closed (FIG. 16), whereby a part of the output current lout and the short-circuit current iK is conducted via the switch S6. Thus, a short-circuit is generated at the time t2 'in the secondary-side output rectifier 5. With the subsequent opening of the switch S5 of the output rectifier 5 at time t3, the flowing negative output current lout is now conducted entirely via the switch S6, which leads to an increase of the primary current (iP + iP ') (FIG. 17).
    After switch S5 of the rectifier 5 has been opened, the transition from the positive passive switching phase to the negative-active switching phase is initiated at time t3 by opening the switch S4, as shown in FIG. At this time, the capacity C4 of the switch S4 is charged and the capacity C3 of the switch S3 is discharged. At time U, the switch S3 is closed without voltage, which in turn switching at zero crossing (ZVS) is realized.
    This is followed, between time U and t5, by the negative active switching phase (Fig.19) until, at time t5, the sign of the primary current ip changes again, thereby initiating the transition from the negative active switching phase to the negative passive switching phase (Fig.20) the transition to the positive active switching phase follows, whereby the accumulated switching cycle is completed.
    The switches S1, S2 are switched in the blocking mode BM with a very short duty cycle D, as explained with reference to FIG. 12, and the switch-on time of the switches S5, S6 is synchronized with the switches S1, S2, as described above. The switch-on time of the switch S6 is again selected in the range of the switching delay V between the switches S1, S2. For the blocking mode BM, it is advantageous if the switch-on time of the switch S6 is selected during the positive passive switching phase in the period from t2 to t3, but not in the positive active switching phase when voltage is applied to the primary side of the transformer T. This applies analogously to the negative passive phase and also to the control of the switch S5 for the blocking mode BM.
    In order to ensure a safe transition from normal operation to the blocking mode BM, and vice versa, a controlled transition is advantageous. For the transition from normal operation into the blocking mode BM, the switch-on duration of the switches S1, S2 is reduced as described above. The transition from the lock mode BM to the normal operation of the full-bridge DC / DC converter 1 is explained below by way of example with reference to FIG.
    If you want to switch from the lock mode BM directly in full load of the full bridge DC / DC converter 1, then this can be achieved simply by the duty cycle D of the switches S1, S2 is increased again until the target on-time of 50 % (minus necessary dead times) is reached. This is shown in Fig. 21 with the mode M1.
    If a lower load L is sought when switching to normal operation, then this would be achieved with the mode M1 even before reaching the desired 50% duty cycle. Therefore, in this case, the mode M2 will be selected as shown in FIG. In this case, the switch-on times of the switches S1, S2 are set earlier in time, e.g. by a period of time Et, which simultaneously sets the switch-on times of the switches S5, S6 in the output rectifier 5 (which are synchronized to the switches S1, S2) earlier. This would shorten the active switching phases of the full-bridge DC / DC converter 1, which would lead to a reduction of the output voltage. This forces the control unit S of the full-bridge DC / DC converter 1 to correct the phase position PS to achieve the target output voltage. This can now be repeated until the desired duty cycle of 50% is reached. By means of the control unit S, the phase position PS required for this purpose is set.
    权利要求:
    Claims (8)
    [1]
    1. A method for controlling a full bridge DC / DC converter (1) having a primary side full bridge (2) and a secondary side output rectifier (5), which are interconnected by a transformer (T), wherein the full bridge (2) arranged in the two bridge branches (3a, 3b), two series-connected switches (S1, S2, S3, S4) successively in succession and repeatedly through a positive active phase, a positive passive phase, a negative active phase and a negative passive phase is, with alternating active and passive phases, characterized in that prior to switching to a passive phase in the secondary side output rectifier (5) a short circuit is generated by the resulting short-circuit current (ik) on the secondary side of the transformer (T) an increase of the Primär¬ current (ip) via the primary side of the transformer (T) causes.
    [2]
    2. The method according to claim 1, characterized in that the short circuit in the output rectifier (5) is canceled before switching to a subsequent active phase.
    [3]
    3. The method according to claim 2, characterized in that the short circuit is maintained during the passive phase.
    [4]
    A method according to any one of claims 1 to 3, characterized in that the short circuit is generated after the termination of the preceding active phase.
    [5]
    5. The method according to any one of claims 1 to 4, characterized in that for ei¬nen transition into a blocking mode (BM) of the full bridge DC / DC converter (1), the switch-on duration of the switches (S1, S2, S3, S4 ) of the first bridge branch (3a) or the second bridge branch (3b) is reduced.
    [6]
    6. The method according to claim 5, characterized in that in the blocking mode (BM), the short circuit in the secondary-side output rectifier (5) is generated during a passive phase.
    [7]
    7. The method according to claim 5 or 6, characterized in that for a transition from the lock mode (BM) in a normal operation of the full bridge DC / DC converter (1), the turn-on of the switch (S1, S2, S3, S4) of the first bridge branch (3a) or the second bridge branch (3b) is increased.
    [8]
    8. The method according to claim 5 or 6, characterized in that for a transition from the lock mode (BM) in a normal operation of the full bridge DC / DC converter (1), the switch-on of the switches (S1, S2, S3, S4) of the first bridge branch (3a) or the second bridge branch (3b) are set earlier in time.
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    LU101923B1|2022-01-03|Boost converter for a power supply for an electrical load, and power supply and method for boosting the input voltage in a power supply for an electrical load
    同族专利:
    公开号 | 公开日
    DE112014005840A5|2016-08-25|
    WO2015091373A1|2015-06-25|
    US20160329822A1|2016-11-10|
    US9906148B2|2018-02-27|
    AT515242B1|2020-04-15|
    引用文献:
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    US5563775A|1994-06-16|1996-10-08|Reliance Comm/Tech Corporation|Full bridge phase displaced resonant transition circuit for obtaining constant resonant transition current from 0° phase angle to 180° phase angle|
    US6185111B1|1999-03-25|2001-02-06|Matsushita Electric Industrial Co., Ltd.|Switching power supply apparatus|
    US20040136209A1|2003-01-09|2004-07-15|Renesas Technology Corp.|Switching power supply device and the semiconductor integrated circuit for power supply control|
    JP2005110384A|2003-09-30|2005-04-21|Hitachi Ltd|Dc-dc converter|
    JP2005224012A|2004-02-05|2005-08-18|Honda Motor Co Ltd|Dc-dc converter|
    US20090129123A1|2006-04-26|2009-05-21|Thales|Insulated power transfer device|
    WO2007145388A1|2006-06-15|2007-12-21|Pstek Co.Ltd.|Method for series resonant converter control with synchronous rectifier|
    US20130223103A1|2012-02-24|2013-08-29|Majid Pahlevaninezhad|Load adaptive variable frequency phase-shift full-bridge dc/dc converter|DE102019101748A1|2019-01-24|2020-07-30|Brusa Elektronik Ag|Bridge circuit and method for operating a bridge circuit|WO2005015716A2|2003-08-09|2005-02-17|Astec International Limited|Soft switched zero voltage transition full bridge converter|
    US8717783B2|2009-10-30|2014-05-06|Delta Electronics Co., Ltd.|Method and apparatus for regulating gain within a resonant converter|
    JP5530212B2|2010-02-10|2014-06-25|株式会社日立製作所|Power supply device, hard disk device, and switching method of power supply device|
    CN102291002B|2011-08-09|2014-11-12|联合汽车电子有限公司|Control method of phase-shifted full-bridge circuit|
    US9515562B2|2013-03-05|2016-12-06|Futurewei Technologies, Inc.|LLC resonant converters|FR3033102B1|2015-02-20|2018-05-11|Devialet|DECOUPAGE POWER SUPPLY WITH CONTROLLED BRANCHES|
    CN106451471B|2015-08-13|2021-03-02|伊顿制造（格拉斯哥）有限合伙莫尔日分支机构|Short-circuit control method and short-circuit control device for power supply device|
    CN108736698A|2017-04-13|2018-11-02|台达电子工业股份有限公司|Power supply unit and residual voltage charging method|
    CN110620512B|2018-06-20|2020-09-15|台达电子工业股份有限公司|Resonant converter and control method|
    法律状态:
    优先权:
    申请号 | 申请日 | 专利标题
    ATA50845/2013A|AT515242B1|2013-12-20|2013-12-20|Method of controlling a full bridge DC / DC converter|ATA50845/2013A| AT515242B1|2013-12-20|2013-12-20|Method of controlling a full bridge DC / DC converter|
    DE112014005840.8T| DE112014005840A5|2013-12-20|2014-12-15|Method for controlling a full bridge DC / DC converter|
    PCT/EP2014/077792| WO2015091373A1|2013-12-20|2014-12-15|Method for controlling a full-bridge dc-dc converter|
    US15/105,690| US9906148B2|2013-12-20|2014-12-15|Method for controlling a full-bridge DC-dc converter|
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